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(R)
September 1998
NT UCT ROD EME TE P EPLAC5 r at R 0 OLE ente OBS ENDED, HFA11pport C m/tsc 2 OMMFA110 nical Su tersil.co H REC ech ww.in T our L or w I tact con INTERS or 881-8
HFA1106
315MHz, Low Power, Video Operational Amplifier with Compensation Pin
Description
The HFA1106 is a high speed, low power current feedback operational amplifier built with Intersil's proprietary complementary bipolar UHF-1 process. This amplifier features a compensation pin connected to the internal high impedance node, which allows for implementation of external clamping or bandwidth limiting. Bandwidth limiting is accomplished by connecting a capacitor (CCOMP) and series damping resistor (RCOMP) from pin 8 to ground. Amplifier performance for various values of CCOMP is documented in the Electrical Specifications. The HFA1106 is ideal for noise critical wideband applications. Not only can the bandwidth be limited to minimize broadband noise, the HFA1106 is optimized for lower feedback resistors (R F = 100 for AV = +2) than most current feedback amplifiers. The low feedback resistor reduces the inverting input noise current contribution to total output noise, while reducing DC errors as well. Please see the "Application Information" section for details.
Features
* Compensation Pin for Bandwidth Limiting * Lower Lot-to-Lot Variability With External Compensation * High Input Impedance . . . . . . . . . . . . . . . . . . . . . . . 1M * Differential Gain . . . . . . . . . . . . . . . . . . . . . . . . . . 0.02% * Differential Phase . . . . . . . . . . . . . . . . . . 0.05 Degrees * Wide -3dB Bandwidth . . . . . . . . . . . . . . . . . . . . 315MHz * Very Fast Slew Rate. . . . . . . . . . . . . . . . . . . . . . 700V/s * Low Supply Current. . . . . . . . . . . . . . . . . . . . . . . 5.8mA * Gain Flatness (to 100MHz) . . . . . . . . . . . . . . . . . 0.1dB
Applications
* Noise Critical Applications * Professional Video Processing * Medical Imaging * Video Digitizing Boards/Systems * Radar/IF Processing * Hand Held and Miniaturized RF Equipment * Battery Powered Communications * Flash A/D Drivers * Oscilloscopes and Analyzers
Part Number Information
PART NUMBER (BRAND) HFA1106IP HFA1106IB (H1106I) HFA11XXEVAL TEMP. RANGE (oC) -40 to 85 -40 to 85 PACKAGE 8 Ld PDIP 8 Ld SOIC PKG. NO. E8.3 M8.15
DIP Evaluation Board for High Speed Op Amps
Pinout
HFA1106 (PDIP, SOIC) TOP VIEW
NC -IN +IN V1 2 3 4 8 COMP V+ OUT NC
+ 6 5
-
7
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2002. All Rights Reserved 3-28
File Number
3922.2
HFA1106
Absolute Maximum Ratings
Voltage Between V+ and V- . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11V DC Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . VSUPPLY Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8V Output Current (Note 1) . . . . . . . . . . . . . . . . Short Circuit Protected 30mA Continuous 60mA 50% Duty Cycle ESD Rating. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . >600V
Thermal Information
Thermal Resistance (Typical, Note 2)
JA (oC/W)
PDIP Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 130 SOIC Package. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 170 Maximum Junction Temperature (Die Only) . . . . . . . . . . . . . . . 175oC Maximum Junction Temperature (Plastic Package) . . . . . . . . 150oC Maximum Storage Temperature Range . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s). . . . . . . . . . . . 300oC (SOIC - Lead Tips Only)
Operating Conditions
Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
NOTES: 1. Output is short circuit protected to ground. Brief short circuits to ground will not degrade reliability; however, continuous (100% duty cycle) output current must not exceed 30mA for maximum reliability. 2. JA is measured with the component mounted on an evaluation PC board in free air.
Electrical Specifications
PARAMETER INPUT CHARACTERISTICS Input Offset Voltage
VSUPPLY = 5V, AV = +1, RF = 510, CCOMP = 0pF, RL = 100 , Unless Otherwise Specified TEST CONDITIONS (NOTE 3) TEST LEVEL TEMP. (oC) MIN TYP MAX UNITS
A A
25 Full Full 25 85 -40 25 85 -40 25 Full Full 25 85 -40 25 85 -40 25 Full Full 25 85 -40 25 85 -40
47 45 45 50 47 47 0.8 0.5 0.5 -
2 3 1 50 48 48 54 50 50 6 10 5 0.5 0.8 0.8 1.2 0.8 0.8 2 5 60 3 4 4 2 4 4
5 8 10 15 25 60 1 3 3 7.5 15 200 6 8 8 5 8 8
mV mV V/oC dB dB dB dB dB dB A A nA/ oC A/V A/V A/V M M M A A nA/ oC A/V A/V A/V A/V A/V A/V
Average Input Offset Voltage Drift Input Offset Voltage Common-Mode Rejection Ratio VCM = 1.8V VCM = 1.8V VCM = 1.2V Input Offset Voltage Power Supply Rejection Ratio VPS = 1.8V VPS = 1.8V VPS = 1.2V Non-Inverting Input Bias Current
B A A A A A A A A
Non-Inverting Input Bias Current Drift Non-Inverting Input Bias Current Power Supply Sensitivity VPS = 1.8V VPS = 1.8V VPS = 1.2V Non-Inverting Input Resistance VCM = 1.8V VCM = 1.8V VCM = 1.2V Inverting Input Bias Current
B A A A A A A A A
Inverting Input Bias Current Drift Inverting Input Bias Current Common-Mode Sensitivity VCM = 1.8V VCM = 1.8V VCM = 1.2V Inverting Input Bias Current Power Supply Sensitivity VPS = 1.8V VPS = 1.8V VPS = 1.2V
B A A A A A A
3-29
HFA1106
Electrical Specifications
PARAMETER Inverting Input Resistance Input Capacitance Input Voltage Common Mode Range (Implied by VIO CMRR, +RIN, and -IBIAS CMS Tests) Input Noise Voltage Density f = 100kHz VSUPPLY = 5V, AV = +1, RF = 510, CCOMP = 0pF, RL = 100 , Unless Otherwise Specified (ContinTEST CONDITIONS (NOTE 3) TEST LEVEL C C A A B B B TEMP. (oC) 25 25 25, 85 -40 25 25 25 MIN 1.8 1.2 TYP 60 1.6 2.4 1.7 3.5 2.5 20 MAX UNITS pF V V nV/Hz pA/Hz pA/Hz
Non-Inverting Input Noise Current Density f = 100kHz Inverting Input Noise Current Density TRANSFER CHARACTERISTICS Open Loop Transimpedance Gain AC CHARACTERISTICS AV = -1 f = 100kHz
C
25
-
500
-
k
AV = +2, RF = 100, RCOMP = 51, Unless Otherwise Specified CC = 0pF CC = 2pF CC = 5pF B B B B B B B B B B B B A 25 25 25 25 25 25 25 25 25 25 25 25 Full 250 140 65 185 110 55 45 25 13 60 15 11 1 315 170 80 245 140 70 65 40 17 100 30 14 MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz V/V
-3dB Bandwidth (AV = +1, RF = 150, VOUT = 0.2VP-P)
-3dB Bandwidth (AV = +2, VOUT = 0.2VP-P)
CC = 0pF CC = 2pF CC = 5pF
0.1dB Flat Bandwidth (AV = +1, RF = 150, VOUT = 0.2VP-P)
CC = 0pF CC = 2pF CC = 5pF
0.1dB Flat Bandwidth (AV = +2, VOUT = 0.2VP-P)
CC = 0pF CC = 2pF CC = 5pF
Minimum Stable Gain OUTPUT CHARACTERISTICS Output Voltage Swing
AV = +2, RF = 100, RCOMP = 51, Unless Otherwise Specified AV = -1, RF = 510 A A 25 Full 25, 85 -40 25 25 25 25 25 25 25 25 25 25 25 25 25 25 3 2.8 50 28 -45 -42 -38 -50 -48 -48 -42 -38 -34 -46 -52 -50 3.4 3 60 42 0.07 90 -53 -48 -44 -57 -56 -56 -46 -42 -38 -57 -57 -57 V V mA mA mA dBc dBc dBc dBc dBc dBc dBc dBc dBc dBc dBc dBc
Output Current
AV = -1, RL = 50, RF = 510 DC AV = -1 CC = 0pF CC = 2pF CC = 5pF
A A B B B B B B B B B B B B B B
Closed Loop Output Impedance Output Short Circuit Current Second Harmonic Distortion (10MHz, VOUT = 2VP-P)
Third Harmonic Distortion (10MHz, VOUT = 2VP-P)
CC = 0pF CC = 2pF CC = 5pF
Second Harmonic Distortion (20MHz, VOUT = 2VP-P)
CC = 0pF CC = 2pF CC = 5pF
Third Harmonic Distortion (20MHz, VOUT = 2VP-P)
CC = 0pF CC = 2pF CC = 5pF
3-30
HFA1106
Electrical Specifications
PARAMETER TRANSIENT CHARACTERISTICS VSUPPLY = 5V, AV = +1, RF = 510, CCOMP = 0pF, RL = 100 , Unless Otherwise Specified (ContinTEST CONDITIONS (NOTE 3) TEST LEVEL TEMP. (oC) MIN TYP MAX UNITS
AV = +2, RF = 100, R COMP = 51 , Unless Otherwise Specified CC = 0pF CC = 2pF CC = 5pF B B B B B B B B B B B B B B B B B B B B B B B B B B B B 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 580 400 470 300 320 200 750 500 550 350 380 250 2.6 3.7 5.2 2.7 3.9 5.9 1.5 6 4 2 6.5 2.5 680 545 530 410 365 300 910 720 730 520 485 375 26 33 49 8.5 2.9 4.2 6.2 3.2 4.4 6.9 4 10 7.5 5 12 7.5 35 43 75 ns ns ns ns ns ns % % % % % % V/s V/s V/s V/s V/s V/s V/s V/s V/s V/s V/s V/s ns ns ns ns
Rise and Fall Times (VOUT = 0.5VP-P, AV = +1, RF = 150)
Rise and Fall Times (VOUT = 0.5VP-P, AV = +2)
CC = 0pF CC = 2pF CC = 5pF
Overshoot (Note 4) VOUT = 250mVP-P (AV = +1, RF = 150, VIN tRISE = 2.5ns) VOUT = 2VP-P VOUT = 0V to 2V Overshoot (Note 4) (AV = +2, VIN tRISE = 2.5ns) VOUT = 250mVP-P VOUT = 2VP-P VOUT = 0V to 2V Slew Rate (VOUT = 4VP-P, AV = +1, RF = 150) +SR, CC = 0pF -SR, C C = 0pF +SR, CC = 2pF -SR, C C = 2pF +SR, CC = 5pF -SR, C C = 5pF Slew Rate (VOUT = 5VP-P, AV = +2) +SR, CC = 0pF -SR, C C = 0pF +SR, CC = 2pF -SR, C C = 2pF +SR, CC = 5pF -SR, C C = 5pF Settling Time (VOUT = +2V to 0V Step, CC = 0pF to 5pF) Overdrive Recovery Time To 0.1% To 0.05% To 0.02% VIN = 2V
VIDEO CHARACTERISTICS AV = +2, RF = 100, RCOMP = 51, Unless Otherwise Specified Differential Gain (f = 3.58MHz, RL = 150) Differential Phase (f = 3.58MHz, RL = 150) POWER SUPPLY CHARACTERISTICS Power Supply Range Power Supply Current C A A NOTES: 3. Test Level: A. Production Tested; B. Typical or Guaranteed Limit Based on Characterization; C. Design Typical for Information Only. 4. Undershoot dominates for output signal swings below GND (e.g. 2VP-P) yielding a higher overshoot limit compared to the VOUT = 0V to 2V condition. 25 25 Full 4.5 5.8 5.9 5.5 6.1 6.3 V mA mA CC = 0pF CC = 5pF CC = 0pF CC = 5pF B B B B 25 25 25 25 0.02 0.02 0.05 0.07 % % Degrees Degrees
3-31
HFA1106 Application Information
Optimum Feedback Resistor All current feedback amplifiers (CFAs) require a feedback resistor (R F) even for unity gain applications, and RF in conjunction with the internal compensation capacitor sets the dominant pole of the frequency response. Thus the amplifier's bandwidth is inversely proportional to RF. The HFA1106 design is optimized for RF = 150 at a gain of +1. Decreasing RF decreases stability resulting in excessive peaking and overshoot - Note: Capacitive feedback causes the same problems due to the feedback impedance decrease at higher frequencies. At higher gains, however, the amplifier is more stable, so RF can be decreased in a trade-off of stability for bandwidth (e.g., RF = 100 for AV = +2). Why Use Externally Compensated Amplifiers? Externally compensated op amps were originally developed to allow operation at gains below the amplifier's minimum stable gain. This enabled development of non-unity gain stable op amps with very high bandwidth and slew rates. Users needing lower closed loop gains could stabilize the amplifier with external compensation if the associated performance decrease was tolerable. With the advent of CFAs, unity gain stability and high performance are no longer mutually exclusive, so why offer unity gain stable op amps with compensation pins? The main reason for external compensation is to allow users to tailor the amplifier's performance to their specific system needs. Bandwidth can be limited to the exact value required, thereby eliminating excess bandwidth and its associated noise. A compensated op amp is also more predictable; lower lot-to-lot variation requires less system overdesign to cover process variability. Finally, access to the internal high impedance node allows users to implement external output limiting or allows for stabilizing the amplifier when driving large capacitive loads. Noise Advantages - Uncompensated The HFA1106 delivers lower broadband noise even without an external compensation capacitor. Package capacitance present at the Comp pin stabilizes the op amp, so lower value feedback resistors can be used. A smaller value RF minimizes the noise voltage contribution of the amplifier's inverting input noise current - INI x R F , usually a large contributor on CFAs - and minimizes the resistor's thermal noise contribution (4KTRF). Figure 1 details the HFA1105 broadband noise performance in its recommended configuration of A V = +2, and RF = 510. Adding a Comp pin to the HFA1105 (thereby creating the HFA1106) yields the 23% noise reduction shown in Figure 2. In both cases, the scope bandwidth, 100MHz, limits the measurement range to prevent amplifier bandwidth differences from affecting the results.
EN = 350 VRMS
EN = 456 VRMS
FIGURE 1. HFA1105 NOISE PERFORMANCE, AV = +2, RF = 510
FIGURE 2. HFA1106 NOISE PERFORMANCE, UNCOMPENSATED, AV = +2, RF = 100
Offset Advantage An added advantage of the lower value RF is a smaller DC output offset. The op amp's inverting input bias current (IBI) flows through the feedback resistor and generates an offset voltage error defined by:
V E = I BI x R F ; and V OS = AV ( VIO ) V E
Reducing R F reduces these errors. Bandwidth Limiting The HFA1106 bandwidth may be limited by connecting a resistor, RCOMP (required to damp the interaction between the compensation capacitor and the package parasitics), and capacitor, C COMP , in series from pin 8 to GND. Typical performance characteristics for various C COMP values are listed in the specification table. The HFA1106 is already unity gain stable, so the main reason for limiting the bandwidth is to reduce the broadband noise. Noise Advantages - Compensated System noise reduction is maximized by limiting the op amp to the bandwidth required for the application. Noise increases as the square root of the bandwidth increase (4x bandwidth increase yields 2x noise increase), so eliminating excess
3-32
HFA1106
bandwidth significantly reduces system noise. Figure 3 illustrates the noise performance of the HFA1106 with its bandwidth limited to 40MHz by a 10pF CCOMP. As expected the noise decreases by approximately 37% (100% x (1-40MHz/100MHz)) compared with Figure 2. The decrease is an even more dramatic 48% versus the HFA1105 noise level in Figure 1. enough, instability. To reduce this capacitance, the designer should remove the ground plane under traces connected to -IN, and keep connections to -IN as short as possible. An example of a good high frequency layout is the Evaluation Board shown in Figure 4.
Evaluation Board
The performance of the HFA1106 may be evaluated using the HFA11XX Evaluation Board. Figure 4 details the evaluation board layout and schematic. Connecting R COMP and C COMP in series from socket pin 8 to the GND plane compensates the op amp. Cutting the trace from pin 8 to the VH connector removes the stray parallel capacitance, which would otherwise affect the evaluation. Additionally, the 500 feedback and gain setting resistors should be changed to the proper value for the gain being evaluated. To order evaluation boards (part number HFA11XXEVAL), please contact your local sales office.
EN = 236 VRMS
FIGURE 3. HFA1106 NOISE PERFORMANCE, COMPENSATED, A V = +2, RF = 100, CC = 10PF
Additionally, compensating the HFA1106 allows the use of a lower value RF for a given gain. The decreased bandwidth due to CCOMP keeps the amplifier stable by offsetting the increased bandwidth from the lower RF . As noted previously, a lower value RF provides the double benefit of reduced DC errors and lower total noise. Less Lot-to-Lot Variability External compensation provides another advantage by allowing designers to set the op amp's performance with a precision external component. On-chip compensation capacitors can vary by 10-20% over the process extremes. A precise external capacitor dominates the on-chip compensation for consistent lot-to-lot performance and more robust designs. Compensating high frequency amplifiers to lower bandwidths can simplify design tasks and ensure long term manufacturability.
+IN
VH
1
OUT VL VGND
V+
TOP LAYOUT
PC Board Layout
This amplifier's frequency response depends greatly on the care taken in designing the PC board. The use of low inductance components such as chip resistors and chip capacitors is strongly recommended, while a solid ground plane is a must! Attention should be given to decoupling the power supplies. A large value (10F) tantalum in parallel with a small value (0.1F) chip capacitor works well in most cases. Terminated microstrip signal lines are recommended at the device's input and output connections. Capacitance, parasitic or planned, connected to the output must be minimized, compensated for by increasing CCOMP , or isolated by a series output resistor. Care must also be taken to minimize the capacitance to ground at the amplifier's inverting input (-IN), as this capacitance causes gain peaking, pulse overshoot, and if large
BOTTOM LAYOUT 510 R1 1 50 IN 0.1F -5V GND 2 3 4 10F 8 7 50 6 5 GND OUT VL 510 VH 0.1F 10F +5V
FIGURE 4. EVALUATION BOARD SCHEMATIC AND LAYOUT
3-33
HFA1106 Typical Performance Curves
AV = +1 CC = 0pF, R F = 150 OUTPUT VOLTAGE (mV)
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified
120 OUTPUT VOLTAGE (mV) 80 40 0 -40 -80 -120
120 80 40 0 -40 -80 -120
AV = +2 CC = 0pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 5. SMALL SIGNAL PULSE RESPONSE
FIGURE 6. SMALL SIGNAL PULSE RESPONSE
1.2 OUTPUT VOLTAGE (V) 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +1 CC = 0pF, RF = 150 OUTPUT VOLTAGE (V)
1.2 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +2 CC = 0pF, R F = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 7. LARGE SIGNAL PULSE RESPONSE
FIGURE 8. LARGE SIGNAL PULSE RESPONSE
3 OUTPUT VOLTAGE (V) 2 1 0 -1 -2 -3
AV = +1 CC = 0pF, RF = 150 OUTPUT VOLTAGE (V)
3 2 1 0 -1 -2 -3
AV = +2 CC = 0pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 9. LARGE SIGNAL PULSE RESPONSE
FIGURE 10. LARGE SIGNAL PULSE RESPONSE
3-34
HFA1106 Typical Performance Curves
NORMALIZED GAIN (dB) CC = 0pF VOUT = 200mVP-P GAIN AV = +2
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
NORMALIZED GAIN (dB)
3 0 -3 -6
0.1 0 -0.1 -0.2 -0.3
AV = +1
CC = 0pF VOUT = 200mVP-P
AV = +1
AV = +2
AV = +1 AV = +2
45 90 135 180
1
10 FREQUENCY (MHz)
100
225 500
PHASE (DEGREES)
PHASE
0
1
10 FREQUENCY (MHz)
100
500
FIGURE 11. FREQUENCY RESPONSE
FIGURE 12. GAIN FLATNESS
3 GAIN (dB) 0 -3 -6
AV = +1 CC = 0pF, RF = 150 VOUT = 200mVP-P GAIN GAIN (dB)
0.1 0 -0.1 -0.2 -0.3 PHASE (DEGREES)
AV = +1 CC = 0pF, RF = 150 VOUT = 200mVP-P
0 PHASE 45 90 135 180 1 10 100 FREQUENCY (MHz) 225 500
1
10 FREQUENCY (MHz)
100
500
FIGURE 13. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 14. GAIN FLATNESS (12 UNITS, 4 RUNS)
3-35
HFA1106 Typical Performance Curves
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
0.2 0.1 0 -0.1 -0.2 -0.3
3 0 -3 -6
AV = +2 CC = 0pF, RF = 100 VOUT = 200mVP-P GAIN
AV = +2 CC = 0pF, RF = 100 VOUT = 200mVP-P
45 90 135 180 1 10 100 FREQUENCY (MHz) 225 500
PHASE (DEGREES)
PHASE
0
1
10 FREQUENCY (MHz)
100
500
FIGURE 15. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 16. GAIN FLATNESS (12 UNITS, 4 RUNS)
120 OUTPUT VOLTAGE (mV) 80 40 0 -40 -80 -120
A V = +1 C C = 2pF, R F = 150 OUTPUT VOLTAGE (mV)
120 80 40 0 -40 -80 -120
AV = +2 CC = 2pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 17. SMALL SIGNAL PULSE RESPONSE
FIGURE 18. SMALL SIGNAL PULSE RESPONSE
1.2 OUTPUT VOLTAGE (V) 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +1 CC = 2pF, R F = 150 OUTPUT VOLTAGE (V)
1.2 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +2 CC = 2pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 19. LARGE SIGNAL PULSE RESPONSE
FIGURE 20. LARGE SIGNAL OUTPUT VOLTAGE
3-36
HFA1106 Typical Performance Curves
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
3 OUTPUT VOLTAGE (V) 2 1 0 -1 -2 -3
AV = +1 CC = 2pF, RF = 150 OUTPUT VOLTAGE (V)
3 2 1 0 -1 -2 -3
AV = +2 CC = 2pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 21. LARGE SIGNAL PULSE RESPONSE
NORMALIZED GAIN (dB)
FIGURE 22. LARGE SIGNAL PULSE RESPONSE
3 0 -3 -6
NORMALIZED GAIN (dB)
CC = 2pF VOUT = 200mVP-P GAIN AV = +2 AV = +1 0 45 90 AV = +2 135 180 1 10 FREQUENCY (MHz) 100 225 500 PHASE (DEGREES) AV = +1
0.1 0 -0.1 -0.2 -0.3
CC = 2pF VOUT = 200mVP-P
AV = +1
AV = +2
PHASE
1
10 100 FREQUENCY (MHz)
500
FIGURE 23. FREQUENCY RESPONSE
FIGURE 24. GAIN FLATNESS
3 GAIN (dB) 0 -3 -6 -9
AV = +1, CC = 2pF, RF = 150 VOUT = 200mVP-P GAIN (dB)
0.1 0 -0.1 -0.2 -0.3
AV = +1, C C = 2pF, RF = 150 VOUT = 200mVP-P
1
10 100 FREQUENCY (MHz)
500
1
10 FREQUENCY (MHz)
100
500
FIGURE 25. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 26. GAIN FLATNESS (12 UNITS, 4 RUNS)
3-37
HFA1106 Typical Performance Curves
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
3 0
AV = +2, CC = 2pF, RF = 100 VOUT = 200mVP-P GAIN
0.1 0 -0.1 -0.2 -0.3
AV = +2, CC = 2pF, RF = 100 VOUT = 200mVP-P
-3 -6 PHASE (DEGREES) PHASE 0 45 90 135 180 1 10 FREQUENCY (MHz) 100 225 500
1
10 FREQUENCY (MHz)
100
500
FIGURE 27. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 28. GAIN FLATNESS (12 UNITS, 4 RUNS)
120 OUTPUT VOLTAGE (mV) 80 40 0 -40 -80 -120
AV = +1 CC = 5pF, R F = 150 OUTPUT VOLTAGE (mV)
120 80 40 0 -40 -80 -120
AV = +2 CC = 5pF, RF = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 29. SMALL SIGNAL PULSE RESPONSE
FIGURE 30. SMALL SIGNAL PULSE RESPONSE
1.2 OUTPUT VOLTAGE (V) 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +1 CC = 5pF, R F = 150 OUTPUT VOLTAGE (V)
1.2 0.8 0.4 0 -0.4 -0.8 -1.2
AV = +2 CC = 5pF, R F = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 31. LARGE SIGNAL PULSE RESPONSE
FIGURE 32. LARGE SIGNAL PULSE RESPONSE
3-38
HFA1106 Typical Performance Curves
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
3 OUTPUT VOLTAGE (V) 2 1 0 -1 -2 -3
AV = +1 CC = 5pF, R F = 150 OUTPUT VOLTAGE (V)
3 2 1 0 -1 -2 -3
AV = +2 CC = 5pF, R F = 100
TIME (10ns/DIV.)
TIME (10ns/DIV.)
FIGURE 33. LARGE SIGNAL PULSE RESPONSE
FIGURE 34. LARGE SIGNAL PULSE RESPONSE
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
3 0
CC = 5pF VOUT = 200mVP-P GAIN
0.1 0 -0.1 -0.2 -0.3
CC = 5pF VOUT = 200mVP-P
-3 -6 PHASE AV = +2
A V = +1
AV = +1 AV = +2
0 AV = +1 45 90 AV = +2 135 180 PHASE (DEGREES)
1
10 FREQUENCY (MHz)
100
225 500
1
10 FREQUENCY (MHz)
100
500
FIGURE 35. FREQUENCY RESPONSE
FIGURE 36. GAIN FLATNESS
3 GAIN (dB) 0 -3 -6
AV = +1 CC = 5pF, RF = 150 VOUT = 200mVP-P GAIN (dB)
0.1 0 -0.1 -0.2 -0.3
AV = +1 CC = 5pF, RF = 150 VOUT = 200mVP-P
0 45 90 135 180 1 10 FREQUENCY (MHz) 100 225 500 PHASE (DEGREES)
1
10 FREQUENCY (MHz)
100
500
FIGURE 37. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 38. GAIN FLATNESS (12 UNITS, 4 RUNS)
3-39
HFA1106 Typical Performance Curves
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
3 0 -3 -6
AV = +2, CC = 5pF, RF = 100 VOUT = 200mVP-P
0.1 0 -0.1 -0.2 -0.3
AV = +2, CC = 5pF, RF = 100 VOUT = 200mVP-P
0 45 90 135 180 1 10 FREQUENCY (MHz) 100 225 500 PHASE (DEGREES)
1
10 FREQUENCY (MHz)
100
500
FIGURE 39. FREQUENCY RESPONSE (12 UNITS, 4 RUNS)
FIGURE 40. GAIN FLATNESS (12 UNITS, 4 RUNS)
4.0 CC = 2pF SETTLING ERROR (%) 0.15 0.1 0.05 0 -0.05 -0.1 CC = 0pF AV = +2 RF = 100 VOUT = 2V OUTPUT VOLTAGE (V) 3.5 AV = -1 |-VOUT| +VOUT |-VOUT| 3.0 +VOUT RL = 100 RL = 50
2.5
0
10
20
30
40
50
60
70
80
90
100
2 -100
-50
0
50
100
150
TIME (ns)
TEMPERATURE (oC)
FIGURE 41. SETTLING RESPONSE
FIGURE 42. OUTPUT VOLTAGE vs TEMPERATURE
3-40
HFA1106 Typical Performance Curves
6.1
VSUPPLY = 5V, TA = 25oC, R L = 100, Unless Otherwise Specified (Continued)
6.0 SUPPLY CURRENT (mA)
5.9
5.8
5.7
5.6
5.5
3.5
4.0
4.5
5.0
5.5
6.0
6.5
7.0
7.5
SUPPLY VOLTAGE (V)
FIGURE 43. SUPPLY CURRENT vs SUPPLY VOLTAGE
Die Characteristics
DIE DIMENSIONS: 59 mils x 58.2 mils x 19 mils 1500m x 1480m x 483m METALLIZATION: Type: Metal 1: AICu(2%)/TiW Thickness: Metal 1: 8kA 0.4kA Type: Metal 2: AICu(2%) Thickness: Metal 2: 16kA 0.8kA PASSIVATION: Type: Nitride Thickness: 4kA 0.5kA TRANSISTOR COUNT: 75 SUBSTRATE POTENTIAL (Powered Up): Floating (Recommend Connection to V-)
Metallization Mask Layout
HFA1106
-IN
COMP
3-41
3-42
3-43

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